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rev. 0.5 december 2012 www.aosmd.com page 1 of 14 AOZ3010PI ezbuck? 2 a synchronous buck regulator general description the AOZ3010PI is a high efficiency, simple to use, 2 a synchronous buck regulator. the AOZ3010PI operates from a 4.5 v to 18 v input voltage range, and provides up to 2 a of continuous output current with an output voltage adjustable down to 0.8 v. the AOZ3010PI comes in an exposed pad so-8 package and is rated over a -40 c to +85 c operating ambient temperature range. features ? 4.5 v to 18 v operating input voltage range ? 80 m ? internal high-side switch and 50 m ? internal low-side switch (at 12 v) ? up to 95 % efficiency ? external soft start ? output voltage adjustable down to 0.8 v ? 2 a continuous output current ? 500 khz pwm operation ? cycle-by-cycle current limit ? pre-bias start-up ? short-circuit protection ? thermal shutdown ? exposed pad so-8 package applications ? point of load dc/dc conversion ? lcd tvs ? set top boxes ? dvd and blu-ray players/recorders ? cable modems typical application figure 1. 3.3 v, 2 a synchronous buck regulator, fs = 500 khz lx vin ss vin vout fb en comp agnd pgnd c2, c3 22f css r1 r2 c1 10f l1 4.7h AOZ3010PI rc cc
AOZ3010PI rev. 0.5 december 2012 www.aosmd.com page 2 of 14 ordering information aos green products use reduced levels of halogens, and are also rohs compliant. please visit www.aosmd.com/media/aosgreenpolicy.pdf for additional information. pin configuration pin description part number ambient temperature range package environmental AOZ3010PI -40 c to +85 c epad so-8 green product pin number pin name pin function 1 pgnd power ground. pgnd needs to be electrically connected to agnd. 2 vin supply voltage input. when vin rises above the uvlo threshold and en is logic high, the device starts up. 3 agnd analog ground. agnd is the reference point for the controller section. agnd needs to be electrically connected to pgnd. 4 fb feedback input. the fb pin is used to set th e output voltage via a resistive voltage divider between the output and agnd. 5 comp external loop compensation pin. connect a rc network between comp and agnd to compensate the control loop. 6 en enable pin. pull en to logic high to enable the device. pull en to logic low to disable the device. if on/off control is not needed, connect it to vin and do not leave it open. 7 ss soft-start pin. 5 a charging current. 8 lx (sense) switching node. this pin has to be ex ternally connected to exposed pad lx through pcb. exposed pad lx switching node. lx is the drain of the in ternal pfet. lx is used as the thermal pad of the power stage. 1 2 3 4 pgnd vin a gnd fb exposed pad so-8 (top view) pad (lx) lx ss en comp 8 7 6 5
AOZ3010PI rev. 0.5 december 2012 www.aosmd.com page 3 of 14 block diagram absolute maximum ratings exceeding the absolute maxi mum ratings may damage the device. note: 1. devices are inherently esd s ensitive, handling precautions are required. human body model rating: 1.5 k ? in series with 100 pf. recommended operating conditions the device is not guaranteed to operate beyond the recommended operating conditions. parameter rating supply voltage (v in ) 20 v lx to agnd -0.7 v to v vin + 0.3 v lx to agnd (20ns) -0.5 v to 22 v en to agnd -0.3 v to v vin + 0.3 v fb, ss, comp to agnd -0.3 v to 6 v pgnd to agnd -0.3 v to + 0.3 v junction temperature (t j ) +150 c storage temperature (t s ) -65 c to +150 c esd rating (1) 2 kv parameter rating supply voltage (v in ) 4.5 v to 18 v output voltage range 0.8 v to 0.85*v in ambient temperature (t a ) -40 c to +85 c package thermal resistance exposed pad so-8 ( ? ja ) 50 c/w 500khz oscillator agnd pgnd vin en fb ss comp lx otp internal +5v ilimit pwm control logic 5v ldo regulator uvlo & por softstart reference & bias 0.8v ss 5a q1 q2 pwm comp level shifter + fet driver isen eamp + ? + ? over-voltage protection comparator + ? + ? + 0.96v
AOZ3010PI rev. 0.5 december 2012 www.aosmd.com page 4 of 14 electrical characteristics t a = 25 c, v in = v en = 12 v, v out = 3.3 v unless otherwise specified (2) note: 2. specification in bold indicate an ambient temperature range of -40 c to +85 c. these specificati ons are guaranteed by design. symbol parameter conditions min. typ. max. units v in supply voltage 4.5 18 v v uvlo input under-voltage lockout threshold v in rising v in falling 4.1 3.7 v i in supply current (quiescent) i out = 0, v fb = 1.2 v, v en > 2 v 1.6 2.5 ma i off shutdown supply current v en = 0 v 110 ? a v fb feedback voltage t a = 25 oc 0.788 0.8 0.812 v load regulation 0.5 % 1% i fb feedback voltage input current 200 na enable v en_off v en_on en input threshold off threshold on threshold 2 0.6 v v en_hys en input hysteresis 200 mv enable leakage current 1 ? a ss time c ss = 16 nf 2 ms modulator f o frequency 400 500 600 khz d max maximum duty cycle 85 % t min controllable minimum on time 150 ns current sense transconductance 7 a / v error amplifier transconductance 200 ? a / v protection i lim current limit 2.5 3.5 a v ovp over-voltage protection off threshold on threshold 960 800 mv over-temperature shutdown limit t j rising t j falling 150 100 c output state high-side switch on-resistance v in = 12 v v in = 5 v 80 120 m ? low-side switch on-resistance v in = 12 v v in = 5 v 50 60 m ?
AOZ3010PI rev. 0.5 december 2012 www.aosmd.com page 5 of 14 typical performance characteristics circuit of figure 1. t a = 25 c, v in = v en = 12 v, v out = 3.3 v unless otherwise specified. light load operation 2s/div start up to full load 1ms/div full load operation 2s/div short circuit protection 10ms/div short circuit recovery 10ms/div vin ripple 0.5v/div vo ripple 0.2v/div vlx 10v/div il 2a/div vin 5v/div vo 2v/div vo 2v/div vlx 10v/div il 2a/div vo 2v/div vlx 10v/div il 2a/div 50% to 100% load transient 100s/div vo ripple 0.2v/div io 2a/div vin ripple 0.2v/div vo ripple 0.2v/div vlx 10v/div il 2a/div
AOZ3010PI rev. 0.5 december 2012 www.aosmd.com page 6 of 14 efficiency detailed description the AOZ3010PI is a current-mode step down regulator with integrated high-side pmos switch and low-side nmos switch. the AOZ3010PI operates from a 4.5 v to 18 v input voltage range and supplies up to 2 a of load current. features include enable control, power-on reset, input under voltage lockout, output over voltage protection, external soft-start, and thermal shut down. the AOZ3010PI is available in an exposed pad so-8 package. enable and soft start the AOZ3010PI has an external soft start feature to limit in-rush current and ensure the output voltage ramps up smoothly to regulation voltage. a soft start process begins when the input voltage rises to 4.1 v and voltage on en pin is high. in soft start process, the fb voltage is ramped to follow the voltage of soft start pin until it reaches 0.8 v. the voltage of soft-start pin is charged by internally 5 a current. the en pin of the AOZ3010PI is active high. connect the en pin to vin if enable function is not used. pulling en to ground will disable the ao z3010pi. do not leave en open. the voltage on en pin must be above 2 v to enable the AOZ3010PI. when the en pin voltage falls below 0.6 v, the AOZ3010PI is disabled. steady-state operation under heavy load steady-state conditions, the converter operates in fixed frequency and continuous-conduction mode (ccm). the AOZ3010PI integrates an internal p-mosfet as the high-side switch. inductor current is sensed by amplifying the voltage drop across the drain to source of the high side power mosfet. output voltage is divided down by the external voltage divider at the fb pin. the difference of the fb pin voltage and reference is amplified by the internal transconductance error amplifier. the error voltage, which shows on the comp pin, is compared against the current signal, which is sum of inductor current signal and ramp compensation signal, at pwm comparator input. if the current signal is less than the error voltage, the internal high-side switch is on. the inductor current flows from the input through the inductor to the output. when the current signal exceeds the error voltage, the high-side switch is off. the inductor current is freewheeling through the internal low-side n-mosfet switch to output. the internal adaptive fet driver guarantees no turn on overlap of both high-side and low- side switch. efficiency (v in = 12v, l = 4.7h) vs. load current 100 95 90 85 80 75 70 65 60 55 50 0 0.5 1.0 1.5 2.0 load current (a) efficiency (%) 5v output 3.3v output 1.8v output 1.2v output
AOZ3010PI rev. 0.5 december 2012 www.aosmd.com page 7 of 14 compared with regulators using freewheeling schottky diodes, the AOZ3010PI uses freewheeling nmosfet to realize synchronous rectification. this greatly improves the converter efficiency and reduces power loss in the low-side switch. the AOZ3010PI uses a p-channel mosfet as the high- side switch. this saves the bootstrap capacitor normally seen in a circuit which is using an nmos switch. it allows 100 % turn-on of the high-side switch to achieve linear regulation mode of operation. the minimum voltage drop from v in to v o is the load current times dc resistance of mosfet plus dc resistance of buck inductor. it can be calculated by equation below: where; v o_max is the maximum output voltage, v in is the input voltage from 4.5 v to 18 v, i o is the output current from 0 a to 2 a, and r ds(on) is the on resistance of the internal mosfet. output voltage programming output voltage can be set by feeding back the output to the fb pin with a resistor divider network. in the application circuit shown in figure 1. the resistor divider network includes r 1 and r 2 . usually, a design is started by picking a fixed r 2 value and calculating the required r 1 with equation below. some standard values of r 1 and r 2 for the most commonly used output voltage values are listed in ta b l e 1 . table 1. combination of r 1 and r 2 should be large enough to avoid drawing excessive current from the output, which will cause power loss. since the switch duty cycle ca n be as high as 100 %, the maximum output voltage can be set as high as the input voltage minus the voltage drop on upper pmos and inductor. protection features the AOZ3010PI has multiple protection features to prevent system circuit damage under abnormal conditions. over current protection (ocp) the sensed inductor current signal is also used for over current protection. since the AOZ3010PI employs peak current mode control, the comp pin voltage is proportional to the peak indu ctor current. the comp pin voltage is limited to be between 0.4 v and 2.5 v internally. the peak inductor current is automatically limited cycle by cycle. when the output is shorted to ground under fault conditions, the inductor current decays very slow during a switching cycle because the output voltage is 0 v. to prevent catastrophic failure, a secondary current limit is designed inside the AOZ3010PI. the measured inductor current is compared against a preset voltage which represents the current limit. when the output current is more than current limit, the high side switch will be turned off. the converter will initiate a soft start once the over- current condition disappears. power-on reset (por) a power-on reset circuit monitors the input voltage. when the input voltage exceeds 4.1 v, the converter starts operation. when input voltage falls below 3.7 v, the converter will be shut down. thermal protection an internal temperature sensor monitors the junction temperature. the sensor shuts down the internal control circuit and high side pmos if the junction temperature exceeds 150 c. the regulator will restart automatically under the control of soft-start circuit when the junction temperature decreases to 100 c. vo (v) r1 (k ? ) r2 (k ? ) 0.8 1.0 open 1.2 4.99 10 1.5 10 11.5 1.8 12.7 10.2 2.5 21.5 10 3.3 31.1 10 5.0 52.3 10 v o_max v in i o r ds on ?? ? ? = v o 0.8 1 r 1 r 2 ------ - + ?? ?? ?? ? =
AOZ3010PI rev. 0.5 december 2012 www.aosmd.com page 8 of 14 application information the basic AOZ3010PI application circuit is shown in figure 1. component selection is explained below. input capacitor the input capacitor must be connected to the v in pin and the gnd pin of the AOZ3010PI to maintain steady input voltage and filter out the pulsing input current. the voltage rating of the input capacitor must be greater than maximum input voltage plus ripple voltage. the input ripple voltage can be approximated by equation below: since the input current is discontinuous in a buck converter, the current stress on the input capacitor is another concern when selecting the capacitor. for a buck circuit, the rms value of input capacitor current can be calculated by: if we let m equal the conversion ratio: the relationship between the input capacitor rms current and voltage conversion ratio is calculated and shown in figure 2. it can be seen that when v o is half of v in , c in is under the worst current stress. the worst current stress on c in is 0.5 x i o . figure 2. i cin vs. voltage conversion ratio for reliable operation and best performance, the input capacitors must have a current rating higher than i cin_rms at the worst operating conditions. ceramic capacitors are preferred for use as input capacitors because of their low esr and high ripple current rating. depending on the application circuits, other low esr tantalum capacitor or aluminum electrolytic capacitor may be used. when selecting ceramic capacitors, x5r or x7r type dielectric ceramic capacitors are preferred for their better temperature and voltage characteristics. note that the ripple current rating from capacitor manufactures are based on a fixed life time. further de- rating may be necessary for practical design requirement. inductor the inductor is used to supply constant current to output when it is driven by a swit ching voltage. for given input and output voltage, inductance and switching frequency together decide the inductor ripple current, which is: the peak inductor current is: high inductance provides a low inductor ripple current but requires larger size inductor to avoid saturation. low ripple current reduces inductor core losses and also reduces rms current through inductor and switches. this results in less conduction loss. usually, peak to peak ripple current on the inductor is designed to be 20 % to 40 % of output current. when selecting the inductor, make sure it is able to handle the peak current without saturation at the highest operating temperature. the inductor takes the highes t current in a buck circuit. the conduction loss on inductor needs to be checked for thermal and efficiency requirements. surface mount inductors in different shape and styles are available from coilcraft, elytone and murata. shielded inductors are small and radiate less emi noise but cost more than unshielded inductors. the choice depends on emi requirement, price and size. ? v in i o fc in ? ----------------- 1 v o v in -------- - ? ?? ?? ?? v o v in -------- - ? ? = i cin_rms i o v o v in -------- - 1 v o v in -------- - ? ?? ?? ?? ? = v o v in -------- - m = 0 0.1 0.2 0.3 0.4 0.5 00.51 m i cin_rms (m) i o ? i l v o fl ? ---------- - 1 v o v in -------- - ? ?? ?? ?? ? = i lpeak i o ? i l 2 -------- + =
AOZ3010PI rev. 0.5 december 2012 www.aosmd.com page 9 of 14 output capacitor the output capacitor is selected based on the dc output voltage rating, output ripple voltage specification and ripple current rating. the selected output capacitor must have a higher rated voltage specification than the maximum desired output voltage including ripple. de-rating needs to be considered for long term reliability. output ripple voltage specification is another important factor for selecting the output capacitor. in a buck converter circuit, output ripple voltage is determined by inductor value, switching frequency, output capacitor value and esr. it can be calculated by the equation below: where, c o is output capacitor value, and esr co is the equivalent series resistance of the output capacitor. when low esr ceramic capacitor is used as output capacitor, the impedance of the capacitor at the switching frequency dominates. output ripple is mainly caused by capacitor value and inductor ripple current. the output ripple voltage calculation can be simplified to: if the impedance of esr at switching frequency dominates, the output ripple voltage is mainly decided by capacitor esr and inductor ripple current. the output ripple voltage calculation can be further simplified to: for lower output ripple voltage across the entire operating temperature range, x5r or x7r dielectric type of ceramic, or other low esr tantalum capacitor or aluminum electrolytic capacitor may also be used as output capacitors. in a buck converter, output capacitor current is continuous. the rms current of output capacitor is decided by the peak to peak inductor ripple current. it can be calculated by: usually, the ripple current rating of the output capacitor is a smaller issue because of the low current stress. when the buck inductor is selected to be very small and inductor ripple current is high, output capacitor could be overstressed. loop compensation the AOZ3010PI employs peak current mode control for ease of use and fast transient response. peak current mode control eliminates the double pole effect of the output l&c filter. it also greatly simplifies the compensation loop design. with peak current mode control, the buck power stage can be simplified to be a one-pole and one-zero system in frequency domain. the pole is dominant pole can be calculated by: the zero is a esr zero due to the output capacitor and its esr. it is can be calculated by: where; c o is the output filter capacitor, r l is load resistor value, and esr co is the equivalent series resistance of output capacitor. the compensation design shapes the converter control loop transfer function for the desired gain and phase. several different types of compensation networks can be used with the AOZ3010PI. for most cases, a series capacitor and resistor network connected to the comp pin sets the pole-zero and is adequate for a stable high-bandwidth control loop. in the AOZ3010PI, fb and comp are the inverting input and the output of the internal error amplifier. a series r and c compensation network connected to comp provides one pole and one zero. the pole is: where; g ea is the error amplifier transconductance, which is 200 x 10 -6 a/v, g vea is the error amplifier voltage gain, which is 500 v/v, and c c is the compensation capacitor in figure 1. ? v o ? i l esr co 1 8 fc o ? ? ------------------------- + ?? ?? ? = ? v o ? i l 1 8 fc o ? ? ------------------------- ?? ?? ? = ? v o ? i l esr co ? = i co_rms ? i l 12 ---------- = f p 1 1 2 ? c o r l ? ? ---------------------------------- - = f z 1 1 2 ? c o esr co ? ? ------------------------------------------------ = f p 2 g ea 2 ? c c g vea ? ? ------------------------------------------ - =
AOZ3010PI rev. 0.5 december 2012 www.aosmd.com page 10 of 14 the zero given by the external compensation network, capacitor c c and resistor r c , is located at: to design the compensation circuit, a target crossover frequency f c to close the loop must be selected. the system crossover frequency is where the control loop has unity gain. the crossover is the also called the converter bandwidth. generally a higher bandwidth means faster response to load transients. however, the bandwidth should not be too high because of system stability concern. when de signing the compensation loop, converter stab ility under all line an d load condition must be considered. usually, it is recommended to set the bandwidth to be equal or less than 1/10 of the switching frequency. the strategy for choosing r c and c c is to set the cross over frequency with r c and set the compensator zero with c c . using selected cr ossover frequency, f c , to calculate r c : where; f c is the desired crossover frequency. for best performance, f c is set to be about 1/10 of the switching frequency; v fb is 0.8v, g ea is the error amplifier transconductance, which is 200 x 10 -6 a/v, and g cs is the current sense circuit transconductance, which is 7 a/v the compensation capacitor c c and resistor r c together make a zero. this zero is put somewhere close to the dominate pole f p1 but lower than 1/5 of the selected crossover frequency. c c can is selected by: the above equation can be simplified to: an easy-to-use application software which helps to design and simulate the compensation loop can be found at www.aosmd.com . thermal management and layout consideration in the AOZ3010PI buck regulator circuit, high pulsing current flows through two circuit loops. the first loop starts from the input capacitors, to the vin pin, to the lx pad, to the filter inductor, to the output capacitor and load, and then return to the input capacitor through ground. current flows in the first loop when the high side switch is on. the second loop starts from inductor, to the output capacitors and load, to the low side nmosfet. current flows in the second loop when the low side nmosfet is on. in pcb layout, minimizing the area of the two loops will reduce the noise of this circuit and improves efficiency. a ground plane is strongly recommended to connect the input capacitor, the output capacitor, and the pgnd pin of the AOZ3010PI. in the AOZ3010PI buck regulator circuit, the major power dissipating components are the AOZ3010PI and the output inductor. the total power dissipation of converter circuit can be measured by input power minus output power: the power dissipation of inductor can be approximately calculated by output current and dcr value of the inductor: the actual junction temperature can be calculated by the power dissipation in the AOZ3010PI and the thermal impedance from junction to ambient: the maximum junction temperature of the AOZ3010PI is 150 oc, which limits the maximum load current capability. please see the thermal de-rating curves for maximum load current of the AOZ3010PI under different ambient temperature. the thermal performance of the AOZ3010PI is strongly affected by the pcb layout. extra care should be taken by users during design process to ensure that the ic will operate under the recommended environmental conditions. f z 2 1 2 ? c c r c ? ? ----------------------------------- = r c f c v o v fb ---------- 2 ? c c ? g ea g cs ? ----------------------------- - ? ? = c c 1.5 2 ? r c f p 1 ? ? ----------------------------------- = c c c o r l ? r c --------------------- = p total_loss v in i in ? ?? v o i o ? ?? ? = p inductor_loss i o 2 r inductor 1.1 ? ? = t junction p total_loss p inductor_loss ? ??? ? ja =
AOZ3010PI rev. 0.5 december 2012 www.aosmd.com page 11 of 14 layout considerations the AOZ3010PI is an exposed pad so-8 package. several layout tips are listed below for the best electric and thermal performance. 1. the exposed pad (lx) is connected to internal pfet and nfet drains. connected a large copper plane to lx pin to help thermal dissipation. 2. do not use thermal relief connection to the vin and the pgnd pin. pour a maximized copper area to the pgnd pin and the vin pin to help thermal dissipa- tion. 3. input capacitor should be connected to the vin pin and the pgnd pin as close as possible. 4. a ground plane is preferred. if a ground plane is not used, separate pgnd from agnd and connect them only at one point to avoid the pgnd pin noise cou- pling to the agnd pin. 5. make the current trace from lx pins to l to co to the pgnd as short as possible. 6. pour copper plane on all unused board area and connect it to stable dc nodes, like vin, gnd or vout. 7. keep sensitive signal trace far away form the lx pad.
AOZ3010PI rev. 0.5 december 2012 www.aosmd.com page 12 of 14 package dimensions, so-8 ep1 notes: 1. package body sizes exclude mold flash and gate burrs. 2. dimension l is measured in gauge plane. 3. tolerance 0.10mm unless otherwise specified. 4. controlling dimension is millimeter, converted inch dimensions are not necessarily exact. 5. die pad exposure size is according to lead frame design. 6. followed from jedec ms-012 symbols a a1 a2 b c d d0 d1 e e e1 e2 e3 l y | l1?l1' | l1 dimensions in millimeters recommended land pattern min. 1.40 0.00 1.40 0.31 0.17 4.80 3.20 3.10 5.80 ? 3.80 2.21 0.40 ? 0 ? d0 unit: mm nom. 1.55 0.05 1.50 0.406 ? 4.96 3.40 3.30 6.00 1.27 3.90 2.41 0.40 ref 0.95 ? 3 0.04 1.04 ref max. 1.70 0.10 1.60 0.51 0.25 5.00 3.60 3.50 6.20 ? 4.00 2.61 1.27 0.10 8 0.12 dimensions in inches d1 e1 e e3 e2 note 5 l1' l1 l gauge plane 0.2500 c d 7 (4x) b 3.70 2.20 2.87 2.71 5.74 1.27 0.80 0.635 e a1 a2 a symbols a a1 a2 b c d d0 d1 e e e1 e2 e3 l y | l1?l1' | l1 min. 0.055 0.000 0.055 0.012 0.007 0.189 0.126 0.122 0.228 ? 0.150 0.087 0.016 ? 0 ? nom. 0.061 0.002 0.059 0.016 ? 0.195 0.134 0.130 0.236 0.050 0.153 0.095 0.016 ref 0.037 ? 3 0.002 0.041 ref max. 0.067 0.004 0.063 0.020 0.010 0.197 0.142 0.138 0.244 ? 0.157 0.103 0.050 0.004 8 0.005
AOZ3010PI rev. 0.5 december 2012 www.aosmd.com page 13 of 14 tape and reel dimensions, so-8 ep1 carrier tape reel tape size 12mm reel size ?330 m ?330.00 0.50 package so-8 (12mm) a0 6.40 0.10 b0 5.20 0.10 k0 2.10 0.10 d0 1.60 0.10 d1 1.50 0.10 e 12.00 0.10 e1 1.75 0.10 e2 5.50 0.10 p0 8.00 0.10 p1 4.00 0.10 p2 2.00 0.10 t 0.25 0.10 n ?97.00 0.10 k0 unit: mm b0 g m w1 s k h n w v r trailer tape 300mm min. or 75 empty pockets components tape orientation in pocket leader tape 500mm min. or 125 empty pockets a0 p1 p2 feeding direction p0 e2 e1 e d0 t d1 w 13.00 0.30 w1 17.40 1.00 h ?13.00 +0.50/-0.20 k 10.60 s 2.00 0.50 g ? r ? v ? leader/trailer and orientation unit: mm
AOZ3010PI rev. 0.5 december 2012 www.aosmd.com page 14 of 14 part marking z3010pi fay part number code assembly lot code year & week code wlt fab & assembly location as used herein: 1. life support devices or systems are devices or systems which, (a) are intended for surgical implant into the body or (b) support or sustain life, and (c) whose failure to perform when properly used in accordance with instructions for use provided in the labeling, can be reasonably expected to result in a significant injury of the user. 2. a critical component in any component of a life support, device, or system whose failure to perform can be reasonably expected to cause the failure of the life support device or system, or to affect its safety or effectiveness. this data sheet contains preliminary data; supplementary data may be published at a later date. alpha & omega semiconductor reserves the right to make changes at any time without notice. life support policy alpha & omega semiconductor products are not authorized for use as critical components in life support devices or systems.

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